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FEATURES Pin Selectable Gains of 10 and 100 True Single Supply Operation Single Supply Range of +2.4 V to +10 V Dual Supply Range of 1.2 V to 6 V Wide Output Voltage Range of 30 mV to 4.7 V Optional Low-Pass Filtering Excellent DC Performance Low Input Offset Voltage: 500 V max Large Common-Mode Range: 0 V to +54 V Low Power: 1.2 mW (VS = +5 V) Good CMR of 90 dB typ AC Performance Fast Settling Time: 24 s (0.01%) Includes Input Protection Series Resistive Inputs (RIN = 200 k ) RFI Filters Included Allows 50 V Continuous Overload APPLICATIONS Current Sensing Interface for Pressure Transducers, Position Indicators, Strain Gages, and Other Low Level Signal Sources PRODUCT DESCRIPTION
Low Cost, Single Supply Differential Amplifier AD626
CONNECTION DIAGRAM 8-Lead Plastic Mini-DIP (N) and SOIC (SO) Packages
200k -IN ANALOG GND -VS 1 1/6 2 G = 30
200k 8 +IN
7
G = 100
3 100k
6
+VS
FILTER
4
G=2
5
OUT
AD626
The AD626 is a low cost, true single supply differential amplifier designed for amplifying and low-pass filtering small differential voltages from sources having a large common-mode voltage. The AD626 can operate from either a single supply of +2.4 V to +10 V, or dual supplies of 1.2 V to 6 V. The input commonmode range of this amplifier is equal to 6 (+VS - 1 V) which provides a +24 V CMR while operating from a +5 V supply. Furthermore, the AD626 features a CMR of 90 dB typ.
160
The amplifier's inputs are protected against continuous overload of up to 50 V, and RFI filters are included in the attenuator network. The output range is +0.03 V to +4.9 V using a +5 V supply. The amplifier provides a preset gain of 10, but gains between 10 to 100 can be easily configured with an external resistor. Furthermore, a gain of 100 is available by connecting the G = 100 pin to analog ground. The AD626 also offers low-pass filter capability by connecting a capacitor between the filter pin and analog ground. The AD626A and AD626B operate over the industrial temperature range of -40C to +85C. The AD626 is available in two 8-lead packages: a plastic mini-DIP and SOIC.
25 INPUT COMMON MODE RANGE - Volts
140
20
100 CMRR - dB 80 60 40 20 0 0.1 G = 10,100 VS = +5V G = 100 VS = 5V
15
VCM FOR SINGLE AND DUAL SUPPLIES
10
G = 10 VS = 5V
5
VCM FOR DUAL SUPPLIES ONLY
0 1 10 100 1k FREQUENCY - Hz 10k 100k 1M
1
2
3
4 Volts
5
POWER SUPPLY VOLTAGE -
Common-Mode Rejection vs. Frequency
Input Common-Mode Range vs. Supply
REV. C
Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781/329-4700 World Wide Web Site: http://www.analog.com Fax: 781/326-8703 (c) Analog Devices, Inc., 1999
AD626-SPECIFICATIONS
SINGLE SUPPLY
Model Parameter GAIN Gain Accuracy Gain = 10 Gain = 100 Over Temperature, TA = TMIN-T MAX Gain Linearity Gain = 10 Gain = 100 OFFSET VOLTAGE Input Offset Voltage vs. Temperature vs. Temperature vs. Supply Voltage (PSR) +PSR -PSR COMMON-MODE REJECTION +CMR Gain = 10, 100 CMR Gain = 10, 100 -CMR Gain = 10, 1001 COMMON-MODE VOLTAGE RANGE +CMV Gain = 10 -CMV Gain = 10 INPUT Input Resistance Differential Common Mode Input Voltage Range (Common Mode) OUTPUT Output Voltage Swing Positive Negative Short Circuit Current +ISC NOISE Voltage Noise RTI Gain = 10 Gain = 100 Gain = 10 Gain = 100 DYNAMIC RESPONSE -3 dB Bandwidth Slew Rate, T MIN to TMAX Settling Time POWER SUPPLY Operating Range Quiescent Current TRANSISTOR COUNT RL = 10 k Gain = 10 Gain = 100 Gain = 10 Gain = 100
(@ +VS = +5 V and TA = +25 C)
Condition Total Error @ VOUT 100 mV dc @ VOUT 100 mV dc G = 10 G = 100 @ VOUT 100 mV dc @ VOUT 100 mV dc AD626A Min Typ Max AD626B Min Typ Max Units
0.4 0.1
1.0 1.0 50 150 0.016 0.02 2.5 2.9 6 74 64 80 55 73
0.2 0.5
0.6 0.6 30 120 0.016 0.02 2.5 2.9 6
% % ppm/C ppm/C % % mV mV V/C dB dB dB dB dB V V
0.014 0.014 1.9
0.014 0.014 1.9
TMIN-TMAX , G = 10 or 100 TMIN-TMAX , G = 10 or 100 74 64 RL = 10 k f = 100 Hz, VCM = +24 V f = 10 kHz, VCM = 6 V f = 100 Hz, VCM = -2 V CMR > 85 dB CMR > 85 dB 66 55 60 80 66 90 64 85 +24 -2
80 66 90 64 85 +24 -2
200 100 6 (VS - l)
200 100 6 (VS - l)
k k V
4.7 4.90 4.7 4.90 0.03 0.03 12
4.7 4.90 4.7 4.90 0.03 0.03 12
V V V V mA
f = 0.1 Hz-10 Hz f = 0.1 Hz-10 Hz f = 1 kHz f = 1 kHz VOUT = +1 V dc Gain = 10 Gain = 100 to 0.01%, 1 V Step TA = TMIN-TMAX Gain = 10 Gain = 100 # of Transistors
2 2 0.25 0.25 100 0.17 0.22 0.1 0.17 24 2.4 5 0.16 0.23 12 0.20 0.29
2 2 0.25 0.25 100 0.17 0.22 0.1 0.17 22 2.4 5 0.16 0.23 10 0.20 0.29
V p-p V p-p V/Hz V/Hz kHz V/s V/s s V mA mA
46
46
NOTES 1 At temperatures above +25C, -CMV degrades at the rate of 12 mV/C; i.e., @ +25C CMV = -2 V, @ +85C CMV = -1.28 V. Specifications subject to change without notice.
-2-
REV. C
DUAL SUPPLY (@ +V =
S
5 V and TA = +25 C)
Condition Total Error RL = 10 k G = 10 G = 100 0.045 0.01 50 TMIN-TMAX , G = 10 or 100 TMIN-TMAX , G = 10 or 100 74 64 RL = 10 k f = 100 Hz, VCM = +24 V f = 10 kHz, VCM = 6 V CMR > 85 dB CMR > 85 dB 66 55 1.0 80 66 90 60 26.5 32.5 74 64 80 55 AD626A Min Typ Max AD626B Min Typ Max
AD626
Units
Model Parameter GAIN Gain Accuracy Gain = 10 Gain = 100 Over Temperature, TA = TMIN-T MAX Gain Linearity Gain = 10 Gain = 100 OFFSET VOLTAGE Input Offset Voltage vs. Temperature vs. Temperature vs. Supply Voltage (PSR) +PSR -PSR COMMON-MODE REJECTION CMR Gain = 10, 100 CMR Gain = 10, 100 COMMON-MODE VOLTAGE RANGE +CMV Gain = 10 -CMV Gain = 10 INPUT Input Resistance Differential Common Mode Input Voltage Range (Common Mode) OUTPUT Output Voltage Swing Positive Negative Short Circuit Current +ISC -ISC NOISE Voltage Noise RTI Gain = 10 Gain = 100 Gain = 10 Gain = 100 DYNAMIC RESPONSE -3 dB Bandwidth Slew Rate, T MIN to TMAX Settling Time POWER SUPPLY Operating Range Quiescent Current TRANSISTOR COUNT
Specifications subject to change without notice.
0.2 0.25
0.5 1.0 50 100 0.055 0.015 500 1.0
0.1 0.15
0.3 0.6 30 80 0.055 0.015 250 0.5
% % ppm/C ppm/C % % V mV V/C dB dB dB dB V V
0.045 0.01 50 0.5 80 66 90 60 26.5 32.5
200 110 6 (VS - 1) RL = 10 k Gain = 10, 100 Gain = 10 Gain = 100
200 110 6 (VS - 1)
k k V
4.7 4.90 1.65 2.1 1.45 1.8 12 0.5
4.7 4.90 1.65 2.1 1.45 1.8 12 0.5
V V V mA mA
f = 0.1 Hz-10 Hz f = 0.1 Hz-10 Hz f = 1 kHz f = 1 kHz VOUT = +1 V dc Gain = 10 Gain = 100 to 0.01%, 1 V Step TA = TMIN-TMAX Gain = 10 Gain = 100 # of Transistors
2 2 0.25 0.25 100 0.17 0.22 0.1 0.17 24 1.2 5 1.5 1.5 6 2 2
2 2 0.25 0.25 100 0.17 0.22 0.1 0.17 22 1.2 5 1.5 1.5 6 2 2
V p-p V p-p V/Hz V/Hz kHz V/s V/s s V mA mA
46
46
REV. C
-3-
AD626
ABSOLUTE MAXIMUM RATINGS 1
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .+36 V Internal Power Dissipation2 Peak Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 60 V Maximum Reversed Supply Voltage Limit . . . . . . . . . . . . -34 V Output Short Circuit Duration . . . . . . . . . . . . . . . . . Indefinite Storage Temperature Range (N, R) . . . . . . . . -65C to +125C Operating Temperature Range AD626A/B . . . . . . . . . . . . . . . . . . . . . . . . . -40C to +85C Lead Temperature Range (Soldering 60 sec) . . . . . . . . +300C
NOTES 1 Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. 2 8-Lead Plastic Package: JA = 100C/W, JC = 50C/W. 8-Lead SOIC Package: JA = 155C/W, JC = 40C/W.
ESD SUSCEPTIBILITY
An ESD classification per method 3015.6 of MIL STD 883C has been performed on the AD626, which is a Class 1 device.
ORDERING GUIDE
Model AD626AN AD626AR AD626BN AD626AR-REEL AD626AR-REEL7
Temperature Range - 40C to +85C - 40C to +85C - 40C to +85C -40C to +85C -40C to +85C
Package Descriptions Plastic DIP Small Outline IC Plastic DIP 13" Tape and Reel 7" Tape and Reel
Package Options N-8 SO-8 N-8
METALIZATION PHOTOGRAPH
Dimensions shown in inches and (mm).
-4-
REV. C
Typical Performance Characteristics-AD626
25 INPUT COMMON MODE RANGE - Volts 6 VS = 5V GAIN = 10, 100 POSITIVE OUTPUT VOLTAGE - Volts 4 Volts 5 5 4 3
20
15
VCM FOR SINGLE AND DUAL SUPPLIES
10
2
1
5
VCM FOR DUAL SUPPLIES ONLY
0 -1
0
1
2
3 SUPPLY VOLTAGE -
10
100 1k LOAD RESISTANCE -
10k
Figure 1. Input Common-Mode Range vs. Supply
Figure 4. Positive Output Voltage Swing vs. Resistive Load
5 POSITIVE OUTPUT VOLTAGE SWING - Volts NEGATIVE OUTPUT VOLTAGE - Volts TA = +25 C 4 SINGLE AND DUAL SUPPLY 3
-6 -5 -4 -3
GAIN = 10
2 DUAL SUPPLY ONLY 1
-2 GAIN = 100 -1
0 1 100
0
0
1
2 3 SUPPLY VOLTAGE - Volts
4
5
1k 10k LOAD RESISTANCE -
100k
Figure 2. Positive Output Voltage Swing vs. Supply Voltage
Figure 5. Negative Output Voltage Swing vs. Resistive Load
-5 NEGATIVE OUTPUT VOLTAGE SWING - Volts TA = +25 C -4 CHANGE IN OFFSET VOLTAGE - V 4 5
30
20
-3
DUAL SUPPLY ONLY
-2
10
-1
0 0 1 2 3 SUPPLY VOLTAGE - Volts
0 0 1 2 3 4 5 WARM-UP TIME - Minutes
Figure 3. Negative Output Voltage Swing vs. Supply Voltage
Figure 6. Change in Input Offset Voltage vs. Warm-Up Time
REV. C
-5-
AD626-Typical Performance Characteristics
1000 100 VS = 5V DUAL SUPPLY CLOSED-LOOP GAIN GAIN = 100 100 COMMON-MODE REJECTION - dB 95
90 85
VS = +5V SINGLE SUPPLY GAIN = 10 10 VS = 5V DUAL SUPPLY
80 VS = 75 70 65 20 5
0 10
100
1k 10k FREQUENCY - Hz
100k
1M
22
24
26
28
30
INPUT COMMON-MODE VOLTAGE - Volts
Figure 7. Closed-Loop Gain vs. Frequency
Figure 10. Common-Mode Rejection vs. Input CommonMode Voltage for Dual Supply Operation
160
100
COMMON-MODE REJECTION - dB
140
G = 10, 100 90
100 CMRR - dB G = 10,100 VS = +5 80 60 40 G = 10 VS = 5 20 0 0.1 G = 100 VS = 5
80
70
1
10
100
1k
10k
100k
1M
60 0 20 40 60 80 INPUT SOURCE RESISTANCE MISMATCH -
FREQUENCY - Hz
Figure 8. Common-Mode Rejection vs. Frequency
Figure 11. Common-Mode Rejection vs. Input Source Resistance Mismatch
100 G = 10, 100 COMMON-MODE REJECTION - dB 95 90 ADDITIONAL GAIN ERROR - %
0.7 CURVE APPLIES TO ALL SUPPLY VOLTAGES AND GAINS BETWEEN 10 AND 100
0.6 0.5 0.4 0.3
85 80 VS = +5 75 70 65 -5
TOTAL GAIN ERROR = GAIN ACCURACY (FROM SPEC TABLE) + ADDITIONAL GAIN ERROR
0.2 0.1 0.0
0
5
10
15
20
25
10
INPUT COMMON-MODE VOLTAGE - Volts
100 SOURCE RESISTANCE MISMATCH -
1k
Figure 9. Common-Mode Rejection vs. Input CommonMode Voltage for Single Supply Operation
Figure 12. Additional Gain Error vs. Source Resistance Mismatch
-6-
REV. C
AD626
0.16 2 V PER VERTICAL DIVISION 5 QUIESCENT CURRENT - mA
0.15 G = 10 0.14
0.13
0.12 1 2 4 3 SUPPLY VOLTAGE - Volts 5 SECONDS PER HORIZONTAL DIVISION
Figure 13. Quiescent Supply Current vs. Supply Voltage for Single Supply Operation
Figure 16. 0.1 Hz to 10 Hz RTI Voltage Noise. VS = 5 V, Gain = 100
2.0
100
80 QUIESCENT CURRENT - mA CLOSED-LOOP GAIN 1.5 FOR VS = 60 5V AND +5V
1.0
40
0.5
20
0
0 1 2 3 SUPPLY VOLTAGE - Volts 4 5 1 10 100 1k 10k VALUE OF RESISTOR RG - 100k 1M
Figure 14. Quiescent Supply Current vs. Supply Voltage for Dual Supply Operation
Figure 17. Closed-Loop Gain vs. RG
10
140 ALL CURVES FOR GAINS OF 10 OR 100
POWER SUPPLY REJECTION - dB
120
Hz
VOLTAGE NSD - V/
1.0 GAIN = 10, 100
100 SINGLE & DUAL -PSRR
80
0.1 VS = 5V DUAL SUPPLY
60 SINGLE +PSRR 40 DUAL DUAL +PSRR +PSRR
0.01
1
10
100 1k FREQUENCY - Hz
10k
100k
20 0.1
1
10
100 1k 10k FREQUENCY - Hz
100k
1M
Figure 15. Noise Voltage Spectral Density vs. Frequency
Figure 18. Power Supply Rejection vs. Frequency
REV. C
-7-
AD626
100 90 100 90
10 0%
10 0%
Figure 19. Large Signal Pulse Response. VS = 5 V, G = 10
Figure 22. Large Signal Pulse Response. VS = +5 V, G = 100
100 90
100 90
10 0%
10 0%
Figure 20. Large Signal Pulse Response. V S = 5 V, G = 100
Figure 23. Settling Time. V S = 5 V, G = 10
100 90
100 90
10 0%
10 0%
Figure 21. Large Signal Pulse Response. V S = +5 V, G = 10
Figure 24. Settling Time. V S = 5 V, G = 100
-8-
REV. C
AD626
ERROR OUT 10k
100 90
10k 2k +VS
INPUT 20V p-p
10k 1k
AD626
10 0%
-VS
Figure 27. Settling Time Test Circuit
THEORY OF OPERATION
Figure 25. Settling Time. V S = +5 V, G = 10
The AD626 is a differential amplifier consisting of a precision balanced attenuator, a very low drift preamplifier (A1), and an output buffer amplifier (A2). It has been designed so that small differential signals can be accurately amplified and filtered in the presence of large common-mode voltages (VCM), without the use of any other active components. Figure 28 shows the main elements of the AD626. The signal inputs at Pins 1 and 8 are first applied to dual resistive attenuators R1 through R4 whose purpose is to reduce the peak commonmode voltage at the input to the preamplifier--a feedback stage based on the very low drift op amp A1. This allows the differential input voltage to be accurately amplified in the presence of large common-mode voltages six times greater than that which can be tolerated by the actual input to A1. As a result, the input CMR extends to six times the quantity (VS - 1 V). The overall common-mode error is minimized by precise laser-trimming of R3 and R4, thus giving the AD626 a common-mode rejection ratio (CMRR) of at least 10,000:1 (80 dB). To minimize the effect of spurious RF signals at the inputs due to rectification at the input to A1, small filter capacitors C1 and C2 are included.
+VS FILTER
100 90
10 0%
Figure 26. Settling Time. VS = +5 V, G = 100
R1 200k +IN
C1 5pF R12 100k A1
AD626
-IN R2 200k R3 41k C2 5pF R4 41k R17 95k R9 10k R10 10k
A2
OUT
R15 10k
R11 10k
R6 500
R5 4.2k
R7 500
R8 10k
R14 555
R13 10k
GND
GAIN = 100
-VS
Figure 28. Simplified Schematic
REV. C
-9-
AD626
The output of A1 is connected to the input of A2 via a 100 k (R12) resistor to facilitate the low-pass filtering of the signal of interest (see Low-Pass Filtering section). The 200 k input impedance of the AD626 requires that the source resistance driving this amplifier be low in value (<1 k)-- this is necessary to minimize gain error. Also, any mismatch between the total source resistance at each input will affect gain accuracy and common-mode rejection (CMR). For example: when operating at a gain of 10, an 80 mismatch in the source resistance between the inputs will degrade CMR to 68 dB. The output buffer, A2, operates at a gain of 2 or 20, thus setting the overall, precalibrated gain of the AD626 (with no external components) at 10 or 100. The gain is set by the feedback network around amplifier A2. The output of amplifier A2 relies on a 10 k resistor to -VS for "pulldown." For single supply operation, (-VS = "GND"), A2 can drive a 10 k ground referenced load to at least +4.7 V. The minimum, nominally "zero," output voltage will be 30 mV. For dual supply operation ( 5 V), the positive output voltage swing will be the same as for a single supply. The negative swing will be to -2.5 V, at G = 100, limited by the ratio:
-VS x R15 + R14 R13 + R14 + R15
+INPUT -IN 200k 200k +IN
-INPUT
1
8
1/6 2 ANALOG GND G = 100 G=30 +VS 6 100k 4 FILTER G= 2 OUT 5 7 NOT CONNECTED
-VS 0.1 F
3
-VS
+VS 0.1 F OUTPUT
AD626
Figure 29. AD626 Configured for a Gain of 10
+INPUT
-INPUT
1
-IN
200k
200k
+IN
8
2
ANALOG GND
1/6 G = 100 G=30 +VS 6 +VS 0.1 F G= 2 OUT 5 OUTPUT 7
-VS 0.1 F
3
-VS 100k FILTER
The negative range can be extended to -3.3 V (G = 100) and -4 V (G = 10) by adding an external 10 k pulldown from the output to -VS. This will add 0.5 mA to the AD626's quiescent current, bringing the total to 2 mA. The AD626's 100 kHz bandwidth at G = 10 and 100 (a 10 MHz gain bandwidth) is much higher than can be obtained with low power op amps in discrete differential amplifier circuits. Furthermore, the AD626 is stable driving capacitive loads up to 50 pF (G10) or 200 pF (G100). Capacitive load drive can be increased to 200 pF (G10) by connecting a 100 resistor in series with the AD626's output and the load.
ADJUSTING THE GAIN OF THE AD626
4
AD626
Figure 30. AD626 Configured for a Gain of 100
+INPUT
-INPUT
1
-IN
200k
200k
+IN
8 RH
2
ANALOG GND
1/6 G = 100 G=30 +VS 6 7
RG +VS 0.1 F
-VS 0.1 F CF FILTER (OPTIONAL)
3
-VS 100k FILTER
The AD626 is easily configured for gains of 10 or 100. Figure 29 shows that for a gain of 10, Pin 7 is simply left unconnected; similarly, for a gain of 100, Pin 7 is grounded, as shown in Figure 30. Gains between 10 and 100 are easily set by connecting a variable resistance between Pin 7 and Analog GND, as shown in Figure 31. Because the on-chip resistors have an absolute tolerance of 20% (although they are ratio matched to within 0.1%), at least a 20% adjustment range must be provided. The values shown in the table in Figure 31 provide a good trade-off between gain set range and resolution, for gains from 11 to 90.
4
G= 2
OUT
5
OUTPUT
AD626
CORNER FREQUENCY OF FILTER = 1 2 CF (100k )
RESISTOR VALUES FOR GAIN ADJUSTMENT
GAIN RANGE 11 - 20 20 - 40 40 - 80 80 - 100
RG( ) 100k 10k 1k 100
RH( ) 4.99k 802 80 2
Figure 31. Recommended Circuit for Gain Adjustment
-10-
REV. C
AD626
SINGLE-POLE LOW-PASS FILTERING BRIDGE APPLICATION
A low-pass filter can be easily implemented by using the features provided by the AD626. By simply connecting a capacitor between Pin 4 and ground, a single-pole low-pass filter is created, as shown in Figure 32.
+INPUT
Figure 34 shows the AD626 in a typical bridge application. Here, the AD626 is set to operate at a gain of 100, using dual supply voltages and offering the option of low-pass filtering.
+VS -IN 200k 200k +IN
1 -INPUT 1 -IN 200k 200k +IN 8 2 G = 100 G=30 +VS 6 100k 4 CF FILTER G= 2 OUT 5 +10V 0.1 F OUTPUT 7 -5V 0.1 F CF OPTIONAL LOW-PASS FILTER 4 3
8
2
ANALOG GND
1/6
ANALOG GND
1/6 G = 100 G=30 +VS 6 +5V 0.1 F G= 2 OUT 5 OUTPUT 7
-VS 100k FILTER
3
-VS
AD626
AD626
Figure 34. A Typical Bridge Application
CORNER FREQUENCY OF FILTER = 1 2 CF (100k )
Figure 32. A One-Pole Low-Pass Filter Circuit Which Operates from a Single +10 V Supply
CURRENT SENSOR INTERFACE
A typical current sensing application, making use of the large common-mode range of the AD626, is shown in Figure 33. The current being measured is sensed across resistor RS . The value of RS should be less than 1 k and should be selected so that the average differential voltage across this resistor is typically 100 mV. To produce a full-scale output of +4 V, a gain of 40 is used adjustable by 20% to absorb the tolerance in the sense resistor. Note that there is sufficient headroom to allow at least a 10% overrange (to +4.4 V).
CURRENT IN CURRENT SENSOR CURRENT OUT RS 1 -IN 200k 200k +IN 8 RH G = 100 G=30 +VS 6 100k 4 FILTER G= 2 OUT 5 7 RG +VS 0.1 F OUTPUT
2
ANALOG GND
1/6
-VS 0.1 F CF OPTIONAL LOW-PASS FILTER
3
-VS
AD626
Figure 33. Current Sensor Interface
REV. C
-11-
AD626
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
8-Lead SOIC (SO-8)
0.1968 (5.00) 0.1890 (4.80)
8 5 4
0.1574 (4.00) 0.1497 (3.80) PIN 1
1
0.2440 (6.20) 0.2284 (5.80)
0.0500 (1.27) BSC 0.0098 (0.25) 0.0040 (0.10) SEATING PLANE 0.0688 (1.75) 0.0532 (1.35) 0.0192 (0.49) 0.0138 (0.35) 8 0.0098 (0.25) 0 0.0075 (0.19)
0.0196 (0.50) 0.0099 (0.25)
45
0.0500 (1.27) 0.0160 (0.41)
8-Lead Plastic Dual-In Line (PDIP) (N-8)
0.430 (10.92) 0.348 (8.84)
8 5
0.280 (7.11) 0.240 (6.10)
1 4
PIN 1 0.100 (2.54) BSC 0.210 (5.33) MAX 0.160 (4.06) 0.115 (2.93) 0.060 (1.52) 0.015 (0.38) 0.130 (3.30) MIN
0.325 (8.25) 0.300 (7.62) 0.195 (4.95) 0.115 (2.93)
0.022 (0.558) 0.070 (1.77) SEATING 0.014 (0.356) 0.045 (1.15) PLANE
0.015 (0.381) 0.008 (0.204)
-12-
REV. C
PRINTED IN U.S.A.
C1627c-0-7/99

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